Power level settings for transmission lines

ABSTRACT

A method, wherein the following steps are iteratively repeated: providing each of a plurality of signals at a respective one of a plurality of transmission links; transmitting each of the plurality of signals over the respective one of the plurality of transmission links; and measuring signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links, wherein an input power level of each of the plurality of signals is set such that the signal-to-noise ratios of the plurality of signals converge when measured after their transmission over the plurality of transmission links.

TECHNICAL FIELD

This invention relates to transmission lines in general and more particularly to power level settings for bundled transmission lines.

BACKGROUND

Telecommunication and broadband services are usually provided to customer premises via twisted pairs of wires. The twisted pairs are often grouped in close proximity into binder groups. Data transmission in these settings may suffer from interference arising from electromagnetic coupling between neighboring twisted pairs, referred to as crosstalk interference.

SUMMARY

A method may comprise the following steps that are iteratively repeated: providing each of a plurality of signals at a respective one of a plurality of transmission links; transmitting each of the plurality of signals over the respective one of the plurality of transmission links; and measuring signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links, wherein an input power level of each of the plurality of signals is set such that the signal-to-noise ratios of the plurality of signals converge when measured after their transmission over the plurality of transmission links.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 schematically illustrates a network of a plurality of transmission lines L₁ to L_(M) according to an embodiment.

FIG. 2 illustrates a model of a transmission system.

FIG. 3 illustrates an interference channel model showing crosstalk interference among the transmission lines L₁ to L_(M).

FIG. 4 illustrates the convergence of an iterative method according to an embodiment.

FIGS. 5A to 5C illustrate exemplary results of a simulation of an iterative method according to an embodiment.

FIGS. 6A to 6C illustrate exemplary results of a simulation of an iterative method according to an embodiment.

FIG. 7 illustrates exemplary results of a simulation of an iterative method according to an embodiment.

FIG. 8 illustrates definitions of variables a and b.

FIG. 9 illustrates exemplary results of a simulation of an iterative method according to an embodiment.

FIG. 10 illustrates frequency band allocation of an exemplary VDSL network.

FIG. 11 illustrates an assumed power spectral density of alien noise.

FIG. 12 illustrates line attenuations of the shortest and the longest transmission line.

FIG. 13 illustrates minimum and maximum FEXT attenuations.

FIG. 14 illustrates exemplary results of a simulation of an iterative method according to an embodiment.

FIG. 15 illustrates exemplary results of a simulation of an iterative method according to an embodiment.

FIG. 16 illustrates spectral power densities for the shortest and the longest transmission line.

FIG. 17 illustrates exemplary results of a simulation of an iterative method according to an embodiment.

DETAILED DESCRIPTION

In the following one or more embodiments are described with reference to the drawings, wherein like reference numerals are generally utilized to refer to like elements throughout, and wherein the various structures are not necessarily drawn to scale. In the following description, for purposes of explanation, numerous specific details are set forth in order to provide a thorough understanding of one or more aspects of embodiments. It may be evident, however, to one skilled in the art that one or more aspects of the embodiments may be practiced with a lesser degree of these specific details. In other instances, known structures and devices are shown in block diagram form in order to facilitate describing one or more aspects of the embodiments. The following description is therefore not to be taken in a limiting sense, and the scope of the invention is defined by the appended claims.

Referring to FIG. 1, a schematic diagram of a network of a plurality of transmission lines L₁ to L_(M) is shown. The transmission lines L₁ to L_(M) are bundled together within a cable C over a length l₀. The network has a central office CO comprising a plurality of transceivers LT₁ to LT_(M) coupled to the respective ends of the transmission lines L₁ to L_(M). At the subscriber premises transceivers RT₁ to RT_(M) are coupled to the other respective ends of the transmission lines L₁ to L_(M). The transceivers RT₁ to RT_(M) may, for example, be modems. Data transmission from the central office CO to a subscriber is called downstream data transmission, whereas data transmission from a subscriber to the central office CO is called upstream data transmission.

According to one embodiment, at least two of the transmission lines L₁ to L_(M) have different lengths. In the network shown in FIG. 1 the length of a transmission line L_(i) is the sum of the length l₀ and a length l_(i) (i=1, . . . , M). The length l₀ is the length over which the transmission lines L₁ to L_(M) are bundled together and occupy the same cable C. The length l_(i) is the length from the end of the cable C to the transceiver RT_(i). Each of the transmission lines L₁ to L_(M) may, for example, be a pair of twisted wires.

According to a further embodiment, the cable C further comprises transmission lines L_(ext), which are not coupled to the central office CO.

According to yet a further embodiment, each of the transmission lines L₁ to L_(M) forms a telecommunication channel. Since voice telephony uses only a small fraction of the bandwidth usually available on the transmission lines L₁ to L_(M), the remaining fraction of the available bandwidth may be used for transmitting data. For data transmission there are a number of services available, such as ISDN (Integrated Services Digital Network) or ADSL (Asymmetric Digital Subscriber Line) or VDSL (Very high bit-rate Digital Subscriber Line) or VDSL2 (Very high bit-rate Digital Subscriber Line 2).

Due to the close proximity of the transmission lines L₁ to L_(M) within the cable C of the length l₀, there is considerable amount of crosstalk interference between different neighboring transmission lines L₁ to L_(M). Physically, there are two types of interference: near-end crosstalk (NEXT) and far-end crosstalk (FEXT).

NEXT refers to interference between neighboring transmission lines L₁ to L_(M) that arises when signals are transmitted in opposite directions. If the neighboring lines carry the same type of service, then the interference is called self-NEXT.

FEXT refers to interference between neighboring transmission lines L₁ to L_(M) that arises when signals are transmitted in the same direction. If the neighboring transmission lines L₁ to L_(M) carry the same type of service, then the interference is called self-FEXT.

Furthermore, noise can be coupled to the transmission lines L₁ to L_(M) that is generated by other sources than neighboring transmission lines L₁ to L_(M). This noise is called alien noise and may, for example, be generated by the transmission lines L_(ext).

In case of NEXT and FEXT, the interfering signals coupled to the transmission lines L₁ to L_(M) depend on the power levels of the signals transmitted over the transmission lines L₁ to L_(M). If signals having the same power level are inputted simultaneously in each of the transmission lines L₁ to L_(M), the signal-to-noise ratio of a transmission line having a longer length will be worse than the signal-to-noise ratio of a shorter transmission line. The reason is that the longer the length of the transmission line, the more the signal transmitted over the transmission line is attenuated.

According to one embodiment, input power levels p(k_(max))₁ to p(k_(max))_(M) for the transmission lines L₁ to L_(M) are determined, which allow the same transmission behavior for all subscribers coupled to the transmission lines L₁ to L_(M). For these purposes, an iterative method is employed with k being the iteration index (k=1, . . . , k_(max)). At each iteration cycle k, signals u(k)₁ to u(k)_(M) are provided to the transmission lines L₁ to L_(M) having input power levels p(k)₁ to p(k)_(M). The signals u(k)₁ to u(k)_(M) are transmitted over the transmission lines L₁ to L_(M) and signals y(k)₁ to y(k)_(M) are received at the other ends of the transmission lines L₁ to L_(M). When receiving the transmitted signals y(k)₁ to y(k)_(M) signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) of the transmitted signals y(k)₁ to y(k)_(M) are measured. The aforementioned steps are iteratively repeated, wherein the input power levels p(k)₁ to p(k)_(M) of the signals u(k)₁ to u(k)_(M) when provided to the transmission lines L₁ to L_(M) are set in such a manner that the signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) converge.

According to a further embodiment, the transmission lines L₁ to L_(M) may be wireless transmission links. When it is referred to transmission lines in the following, the transmission lines may therefore also be replaced by wireless transmission links.

According to a further embodiment, xDSL is used as service for transmitting data over the transmission lines L₁ to L_(M).

According to a further embodiment, signals u(k)₁ to u(k)_(M) are transmitted in upstream direction over the transmission lines L₁ to L_(M).

According to a further embodiment, the iterative method is performed during the initialization of the central office CO.

According to a further embodiment, the input power levels p(k_(max))₁ to p(k_(max))_(M) are used for transmitting further signals u₁ to u_(M) over the transmission lines L₁ to L_(M).

According to a further embodiment, the signals u(k)₁ to u(k)_(M) are statistically selected data modulated on a transmission frequency.

According to a further embodiment, the input power levels p(k+1)₁ to p(k+1)_(M) of the signals u(k+1)₁ to u(k+1)_(M) when provided to the transmission lines L₁ to L_(M) during an iteration cycle k+1 depend on the measured signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) measured during the previous iteration cycle k.

According to a further embodiment, the input power level p(k+1)_(i) of the signal u(k+1)_(i) (i=1, . . . , M) when provided to the transmission line L_(i) during an iteration cycle k+1 is a function F of the difference of the measured signal-to-noise ratio Sn(k)_(i) of the signal y(k)_(i) transmitted over the transmission line L₁ during the previous iteration cycle k and an average value avg of the signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) measured during the previous iteration cycle k:

p(k+1)_(i) =F[Sn(k)_(i)−avg(Sn(k)₁ , . . . , Sn(k)_(M))].  (1)

According to a further embodiment, the input power level p(k+1)_(i) of the signal u(k+1)_(i) (i=1, . . . , M) when provided to the transmission line L_(i) during an iteration cycle k+1 depends on a product having at least a factor F₁ and a factor F₂. The factor F₁ is a function of the input power level p(k)_(i) of the signal u(k)_(i) when provided to the transmission line L_(i) during the previous iteration cycle k. The factor F₂ is a function of the difference of the measured signal-to-noise ratio Sn(k)_(i) of the signal y(k)_(i) transmitted over the transmission line L_(i) during the previous iteration cycle k and an average value avg of the signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) measured during the previous iteration cycle k:

p(k+1)_(i) =F ₁ [p(k)_(i) ]·F ₂ [Sn(k)_(i)−avg(Sn(k)₁ , . . . , Sn(k)_(M))].  (2)

According to a further embodiment, the input power levels p(1)₁ to p(1)_(M) of the signals u(1)₁ to u(1)_(M) at the first iteration cycle (k=1) are predetermined. For example, the input power levels p(1)₁ to p(1)_(M) are set to the highest power level.

According to a further embodiment, the input power level p(2)_(i) of the signal u(2)_(i) (i=1, . . . , M) at the second iteration cycle (k=2) depends on the inverted value of the measured signal-to-noise ratio Sn(1)_(i) of the transmitted signal y(1)_(i) of the first iteration cycle (k=1).

According to another embodiment, a method refers to a plurality of transmission lines L₁ to L_(M) each having an input terminal and an output terminal. Referring to FIG. 1, the input terminals may, for example, be the transceivers LT₁ to LT_(M) of the central office CO and the output terminals may be the transceivers RT₁ to RT_(M) at the subscribers end or vice versa.

According to the method of the present embodiment, first signals u(k)₁ to u(k)_(M) are provided to the input terminals and transmitted over the transmission lines L₁ to L_(M). At the output terminals of the transmission lines L₁ to L_(M) transmitted first signals y(k)₁ to y(k)_(M) are received. Further, signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) of the transmitted first signals y(k)₁ to y(k)_(M) are measured at the output terminals of the transmission lines L₁ to L_(M). Subsequently, second signals u(k+1)₁ to u(k+1)_(M) are provided to the input terminals and are transmitted over the transmission lines L₁ to L_(M). The input power levels p(k+1)₁ to p(k+1)_(M) of the second signals u(k+1)₁ to u(k+1)_(M) are set depending on the measured signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) of the afore transmitted first signals y(k)₁ to y(k)_(M).

The measured signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) of the transmitted first signals y(k)₁ to y(k)_(M) are distributed over a first range of signal-to-noise ratios. The distribution of the measured signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) thus defines the first range. According to one embodiment, the input power levels p(k+1)₁ to p(k+1)_(M) of the second signals u(k+1)₁ to u(k+1)_(M) are set in such a manner that the signal-to-noise ratios Sn(k+1)₁ to Sn(k+1)_(M) of the second signals y(k+1)₁ to y(k+1)_(M) after their transmission over the transmission lines L₁ to L_(M) are distributed over a second range of signal-to-noise ratios which is smaller than the first range. This procedure results in a convergence of the signal-to-noise ratios.

According to another embodiment, a transfer function of each of the transmission lines L₁ to L_(M) is determined and information related to interference characteristics of each of the transmission lines L₁ to L_(M) is collected. Furthermore, the transfer functions and the information related to interference characteristics are used to determine input power levels p₁ to p_(M) of signals u₁ to u_(M) in such a manner that, when providing the signals u₁ to u_(M) to the input terminals of the transmission lines L₁ to L_(M) and measuring the signal-to-noise ratios Sn₁ to Sn_(M) of the transmitted signals y₁ to y_(M) at the output terminals of the transmission lines L₁ to L_(M), the signal-to-noise ratios Sn₁ to Sn_(M) are essentially equal. For example, the signal-to-noise ratios Sn₁ to Sn_(M) are essentially equal if the signal-to-noise ratios Sn₁ to Sn_(M) are within a predetermined range or a predetermined error range.

According to another embodiment, input power levels {tilde over (p)}(0)₁ to {tilde over (p)}(0)_(M) for the transmission lines L₁ to L_(M) are provided. The input power levels {tilde over (p)}(0)₁ to {tilde over (p)}(0)_(M) are provided in such a manner that when signals ũ(0)₁ to ũ(0)_(M) having the input power levels {tilde over (p)}(0)₁ to {tilde over (p)}(0)_(M) are provided to the transmission lines L₁ to L_(M), signals {tilde over (y)}(0)₁ to {tilde over (y)}(0)_(M) are received at the other ends of the transmission lines L₁ to L_(M) having essentially equal signal-to-noise ratios {tilde over (S)}n(0)₁ to {tilde over (S)}n(0)_(M). For example, the input power levels {tilde over (p)}(0)₁ to {tilde over (p)}(0)_(M) resulting in equal signal-to-noise ratios {tilde over (S)}n(0)₁ to {tilde over (S)}n(0)_(M) may be determined by using one of the methods described above. The signal-to-noise ratios {tilde over (S)}n(0)₁ to {tilde over (S)}n(0)_(M) are essentially equal if the signal-to-noise ratios {tilde over (S)}n(0)₁ to {tilde over (S)}n(0)_(M) are within a predetermined range or a predetermined error range.

Subsequently, the following steps are iteratively repeated. Signals ũ(k)₁ to ũ(k)_(M) are provided to the transmission lines L₁ to L_(M) (k=1, 2, . . . ). The signals ũ(k)₁ to ũ(k)_(M) are transmitted over the transmission lines L₁ to L_(M) and signals {tilde over (y)}(k)₁ to {tilde over (y)}(k)_(M) are received at the other ends of the transmission lines L₁ to L_(M). The signal-to-noise ratios {tilde over (S)}n(k)₁ to {tilde over (S)}n(k)_(M) of the transmitted signals {tilde over (y)}(k)₁ to {tilde over (y)}(k)_(M) are measured. At each iteration cycle k+1 the input power level {tilde over (p)}(k+1)_(i) of the signal ũ(k+1)_(i) (i=1, . . . , M−1) is greater than the input power level {tilde over (p)}(k)_(i) of the signal ũ(k)_(i) of the previous iteration cycle k.

According to a further embodiment, the method is terminated or at least interrupted when at least one of the measured signal-to-noise ratios {tilde over (S)}n(k)₁ to {tilde over (S)}n(k)_(M) exceeds a predetermined threshold.

According to a further embodiment, the input power level {tilde over (p)}(k+1)_(i) of the signal ũ(k+1)_(i) (i=1, . . . , M−1) when provided to the transmission line L_(i) during an iteration cycle k+1 depends on a product having at least a factor F₁ and a factor F₂. The factor F₁ is a function of the input power level {tilde over (p)}(k)_(i) of the signal ũ(k)_(i) provided to the transmission line L_(i) during the previous iteration cycle k. The factor F₂ depends on a linear function or an exponential function or a logarithmic function of the input power level {tilde over (p)}(k)_(i) of the signal ũ(k)_(i) of the previous iteration cycle k:

{tilde over (p)}(k+1)_(i) =F ₁ [{tilde over (p)}(k)_(i) ]·F ₂ [{tilde over (p)}(k)_(i)].  (3)

In the following another embodiment is described in more detail. In this embodiment the frequency band used for transmitting signals in downstream direction is different from the frequency band used for transmitting signals in upstream direction. As a consequence, self-NEXT can be excluded as a source of interference, however self-FEXT must be considered. For example, VDSL or ADSL may be used as services for transmitting data over the transmission lines and DMT (Discrete Multi-Tone) modulation may be used for modulating signals, however the embodiment described in the following is not limited thereto. The present embodiment may be also applied to a system which uses the same frequency band, but different time slots for downstream and upstream directions.

The network of the transmission lines L₁ to L_(M) of the present embodiment is shown in FIG. 1. The transceivers LT₁ to LT_(M) of the central office CO as well as the transceivers RT₁ to RT_(M) at the subscriber premises comprise units which allow to measure the signal-to-noise ratios of signals received over the respective transmission lines L₁ to L_(M). The values of the measured signal-to-noise ratios are transferred to a central control unit CCU, which is coupled to the central office CO. The central control unit CCU sets the power levels of the signals transmitted by the transceivers LT₁ to LT_(M) and RT₁ to RT_(M). Special transmission and control channels are provided between the central office CO and the transceivers RT₁ to RT_(M) in order to exchange data between the central control unit CCU and the transceivers RT₁ to RT_(M).

FIG. 2 illustrates a model of the transmission system of the present embodiment. The model only considers the transmission lines L₁ to L_(M) which are coupled to the central office CO. The arrows between the transceivers LT_(i) and RT_(i) illustrate the logical connections between the transceivers LT_(i) and RT_(i) (i=1, . . . , M). Since it is assumed that there is no crosstalk interference between downstream and upstream directions, the power levels in downstream and upstream directions can be determined separately.

As can be seen from FIG. 2, self-FEXT signals fext and interfering signals r disturb the signals transmitted between the transceivers LT_(i) and RT_(i). The interfering signals r are caused by alien noise which may be due to the transmission lines L_(ext), which are not coupled to the central office CO, and other external sources.

In FIG. 3 an interference channel model is illustrated exhibiting crosstalk interference among the transmission lines L₁ to L_(M) in either downstream or upstream direction. A signal u_(i) is provided to the input terminal of a transmission line L_(i) and a signal y_(i) is received at the output terminal of the transmission line L_(i) (i=1, . . . , M). A transfer function H_(ij) is the transfer function of a channel from the input terminal of a transmission line L_(i) to the output terminal of the transmission line L_(j) for a specific frequency channel (j=1, . . . , M). The transfer functions H_(ii) are the transfer functions of the transmission lines L₁ to L_(M) and the transfer functions H_(ij,i≠j) are the crosstalk transfer functions.

According to the interference channel model shown in FIG. 3, the signal y_(i) received at the output terminal of the transmission line L_(i) is as follows:

$\begin{matrix} {y_{i} = {{u_{i} \cdot H_{ii}} + {\sum\limits_{{j = 1},{j \neq i}}^{M}{u_{j} \cdot H_{ij}}} + {r_{i}.}}} & (4) \end{matrix}$

Assuming that the signals transmitted over different transmission lines are not correlated, the signal-to-noise ratio Sn_(i) at the output terminal of the transmission line L_(i), which is the ratio between the power S of the wanted signal and the power N of the noise, is given by the following equation:

$\begin{matrix} {{Sn}_{i} = {\left( \frac{S}{N} \right)_{i} = {\frac{{\langle u^{2}\rangle}_{i} \cdot {H_{ii}}^{2}}{{\sum\limits_{{j = 1},{j \neq i}}^{M}{{\langle u^{2}\rangle}_{j} \cdot {H_{ij}}^{2}}} + {\langle r^{2}\rangle}_{i}}.}}} & (5) \end{matrix}$

Since many signals have a very wide dynamic range, signal-to-noise ratios are usually expressed in terms of the logarithmic decibel scale. In decibels, the logarithmic signal-to-noise ratio Sndb_(i) is 10 times the logarithm of the power ratio Sn_(i):

$\begin{matrix} {{Sndb}_{i} = {10 \cdot {\log_{10}\left( \left( \frac{S}{N} \right)_{i} \right)}}} & (6) \end{matrix}$

In order to be able to transmit high bit rates, the values of the signal-to-noise ratio Sn_(i) should be large. The number e of bits, which can be transmitted per frequency channel and data symbol, is:

$\begin{matrix} {e = {{floor}\left( {\log_{2}\left( {1 + \frac{Sn}{{Sn}_{ref}}} \right)} \right)}} & (7) \end{matrix}$

Sn_(ref) is a reference signal-to-noise ratio, which depends on the wanted bit error rate, the margins and the coding gain.

As can be seen from equation (5), the signal-to-noise ratio Sn_(i) measured at the output terminal of the transmission line L_(i) depends on the power levels of the signals u₁ to u_(M), the transfer function H_(ii), the transfer functions H_(ij,j≠1) and the power level of the alien noise interference signal r_(i). Two extreme cases may arise:

-   (a) FEXT can be neglected compared to alien noise. In this case the     signal-to-noise ratio Sn_(i) only depends on the input power level     of the signal u_(i). In order to achieve a high signal-to-noise     ratio Sn_(i), it is favorable to feed the transmission lines L₁ to     L_(M) with signals u₁ to u_(M) at the highest power level. -   (b) Alien noise can be neglected compared to FEXT. In this case the     signal-to-noise ratio Sn_(i) depends on the input power levels of     all signals u₁ to u_(M). If the signals u₁ to u_(M) have equal input     power levels, shorter transmission lines L_(i) produce better     signal-to-noise ratios Sn_(i).

A conditional equation for the transfer function H_(ij) can be derived:

|H _(ij)(f)|=K _(ij) ·f·√{square root over (l ₀)}·|H _(line)(f)|  (8)

Based on a more realistic model, the following equation was found for the transfer function H_(ij):

$\begin{matrix} {{{H_{ij}(f)}} = {K_{ij} \cdot f \cdot \sqrt{l_{0}} \cdot {{H_{line}(f)}} \cdot \left\lbrack {1 + {3 \cdot {\cos \left( \frac{2 \cdot \pi \cdot l_{0}}{c_{line}} \right)}} - {3 \cdot {\sin \left( \frac{2 \cdot \pi \cdot l_{0}}{c_{line}} \right)}}} \right\rbrack}} & (9) \end{matrix}$

In equations (8) and (9) f is the frequency, l₀ is the length of the cable C which binds the transmission lines L_(i) and L_(j) together, K_(ij) is a frequency- and length-independent factor, which depends on physical and geometrical features of the cable C, H_(line)(f) is the frequency response of the transmission lines L_(i) and L_(j) and c is the speed of light in the transmission lines L_(i) and L_(j), which is roughly 200,000 km/s.

In the following a method is discussed as an exemplary embodiment, which allows to determine the input power levels p₁ to p_(M) for signals provided to the input terminals of the transmission lines L₁ to L_(M) so that the signals received at the output terminals of the transmission lines L₁ to L_(M) exhibit equal signal-to-noise ratios Sn₁ to Sn_(M). As a result the same maximal data rate can be transmitted over the transmission lines L₁ to L_(M). The method is performed either for downstream or for upstream direction and for a single frequency channel.

The input power levels p₁ to p_(M) of the signals provided to the transmission lines L₁ to L_(M), the signal-to-noise ratios Sn₁ to Sn_(M) measured at the output terminals of the transmission lines L₁ to L_(M) and the logarithmic signal-to-noise ratios Sndb₁ to Sndb_(M) are combined in vectors p, Sn and Sndb, respectively:

$\begin{matrix} {p = \begin{bmatrix} p_{1} \\ p_{2} \\ \vdots \\ p_{M} \end{bmatrix}} & (10) \\ {{Sn} = \begin{bmatrix} {Sn}_{1} \\ {Sn}_{2} \\ \vdots \\ {Sn}_{M} \end{bmatrix}} & (11) \\ {{Sndb} = {\begin{bmatrix} {Sndb}_{1} \\ {Sndb}_{2} \\ \vdots \\ {Sndb}_{M} \end{bmatrix}.}} & (12) \end{matrix}$

According to one embodiment, at the first cycle of the method, which is denoted with k=1, signals are simultaneously provided to the transmission lines L₁ to L_(M) having the highest input power level p_(max):

$\begin{matrix} {{p\left( {k = 1} \right)} = \begin{bmatrix} p_{\max} \\ p_{{ma}x} \\ \vdots \\ p_{\max} \end{bmatrix}} & (13) \end{matrix}$

The signal-to-noise ratios Sn(1)₁ to Sn(1)_(M) of the signals, which are received at the output terminals of the transmission lines L₁ to L_(M), are measured. According to a further embodiment, the signal-to-noise ratios Sn(1)₁ to Sn(1)_(M) measured in the first cycle of the method (k=1) are used for determining the input power levels p(k=2) of the second cycle:

$\begin{matrix} {{p\left( {k = 2} \right)} = {\begin{bmatrix} \left( \frac{1}{{{Sn}(1)}_{1}} \right) \\ \left( \frac{1}{{{Sn}(1)}_{2}} \right) \\ \vdots \\ \left( \frac{1}{{{Sn}(1)}_{M}} \right) \end{bmatrix}.}} & (14) \end{matrix}$

According to one embodiment, the vector p(2) is scaled:

$\begin{matrix} {{\hat{p}(2)} = {{p(2)} \cdot \frac{p_{\max}}{\max \left( {p(2)} \right)}}} & (15) \end{matrix}$

In equation (15) max(p(2)) denotes the maximum component of the vector p(2) of equation (14). The scaling prevents exceeding the maximum power level p_(max).

The scaled vector {circumflex over (p)}(2) provides the input power levels for the signals provided to the input terminals of the transmission lines L₁ to L_(M) during the second cycle of the method. At the output terminals of the transmission lines L₁ to L_(M) the signal-to-noise ratios Sn(2)₁ to Sn(2)_(M) or the logarithmic signal-to-noise ratios Sndb(2)₁ to Sndb(2)_(M) are measured. Transmitting signals over the transmission lines L₁ to L_(M) and measuring their signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) or their logarithmic signal-to-noise ratios Sndb(k)₁ to Sndb(k)_(M) is then iteratively repeated.

The iterations are repeated until the measured signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) or the measured logarithmic signal-to-noise ratios Sndb(k)₁ to Sndb(k)_(M) reach sufficient convergence (k=k_(max)). At each of the iteration cycles k=2 to k=k_(max)−1 the signal-to-noise ratios Sn(k)₁ to Sn(k)_(M) or the logarithmic signal-to-noise ratios Sndb(k)₁ to Sndb(k)_(M) of the signals received at the output terminals of the transmission lines L₁ to L_(M) are measured and used for setting the input power levels p(k+1) of the signals provided to the input terminals of the transmission lines L₁ to L_(M) during the next iteration cycle k+1:

p(k+1)=p(k)·|1−g·x(k)|  (16)

In equation (16) g is a predetermined constant, which influences the convergence of the method, and x(k) is calculated as follows:

$\begin{matrix} {{x(k)} = {{{Sndb}(k)} - {\frac{1}{M}{{{\sum\limits_{i = 1}^{M}{{Sndb}(k)}_{i}}}.}}}} & (17) \end{matrix}$

Before the determined input power levels are used for providing signals to the transmission lines L₁ to L_(M), the vector p(k+1) may be scaled:

$\begin{matrix} {{\hat{p}\left( {k + 1} \right)} = {{p\left( {k + 1} \right)} \cdot {\frac{p_{\max}}{\max \left( {p\left( {k + 1} \right)} \right)}.}}} & (18) \end{matrix}$

In equation (18) max(p(k+1)) denotes the maximum component of the vector p(k+1). The scaled vector p(k+1) is used for providing signals to the transmission lines L₁ to L_(M) at the iteration cycle k+1.

In the following a simulation is presented which illustrates the method described above. The simulated network comprises 50 transmission lines L₁ to L₅₀. The lengths of the transmission lines L₁ to L₅₀ are evenly distributed between 200 m and 800 m. The network is based on a model as shown in FIG. 3. FIG. 4 illustrates the convergence of the applied iterative method. In FIG. 4 a difference d(k) is plotted versus the iteration index k. The difference d(k) is the difference between the maximum logarithmic signal-to-noise ratio and the minimum logarithmic signal-to-noise ratio measured at each iteration cycle k:

d(k)=max(Sndb(k))−min(Sndb(k))  (19)

The upper diagram of FIG. 4 shows the difference d(k) on a linear scale, whereas the lower diagram of FIG. 4 shows the difference d(k) on a logarithmic scale. It can be seen from FIG. 4 that the difference d(k) between the maximum logarithmic signal-to-noise ratio and the minimum logarithmic signal-to-noise ratio becomes smaller than 0.01 dB after 6 iteration cycles which means that the logarithmic signal-to-noise ratios measured at the output terminals of the transmission lines L_(i) to L₅₀ have sufficiently converged at this point in time.

FIGS. 5 and 6 show plots of the input power level p versus the length l of the transmission lines and plots of the resulting logarithmic signal-to-noise ratios Sndb versus the length l in the presence of only FEXT (cf. FIGS. 5A and 6A), FEXT and alien noise (cf. FIGS. 5B and 6B) as well as only alien noise (cf. FIGS. 5C and 6C). FIG. 5 refers to signals transmitted in upstream direction and FIG. 6 refers to signals transmitted in downstream direction. Data illustrated by dashed lines were recorded when the maximum power level p_(max) (=0 dB) was used for providing signals to the transmission lines L₁ to L₅₀. Data illustrated by continuous lines were recorded after the iterative method described above had reached convergence (k=k_(max)).

It is evident from FIGS. 5 and 6 that performing the iterative method described above results in a convergence of the signal-to-noise ratios of all transmission lines. It can be further seen from FIGS. 5 and 6 that the more FEXT interference occurs, the more the iterative method leads to an improvement of the signal-to-noise ratios of the long transmission lines, whereas the signal-to-noise ratios of the short transmission lines are decreased due to the iterative method.

Further, a comparison of the FIGS. 5 and 6 reveals that the improvement of the behavior of the longer transmission lines is more striking for the upstream direction than for the downstream direction.

FIG. 7 illustrates the simulated behavior of a further network. The simulated network comprises 50 transmission lines L₁ to L₅₀, the lengths of which are statistically distributed between 200 m and 800 m. Moreover, the factor K_(ij) and the alien noise are also statistically distributed to a certain degree. In FIG. 7 a plot of the input power level p versus the length l of the transmission lines and a plot of the resulting logarithmic signal-to-noise ratio Sndb versus the length l in the presence of FEXT and alien noise are shown. The data shown in FIG. 7 were recorded in upstream direction. Data illustrated by dashed lines were recorded when the maximum input power level p_(max) (=0 dB) was used for the providing signals to the transmission lines L₁ to L₅₀. Data illustrated by continuous lines were recorded after the iterative method had reached convergence.

Since the method according to the embodiment described above improves the signal-to-noise ratios of longer transmission lines especially if FEXT is the dominant source of interference, it is interesting to know a measure of the presence of FEXT compared to alien noise. Such a measure is given by a variable η:

$\begin{matrix} {\eta = \frac{a}{b}} & (20) \end{matrix}$

In equation (20) variables a and b are introduced. The variables a and b are defined as follows:

a=max(Sndb(1))−min(Sndb(k _(max)))  (21)

b=max(Sndb(1))−min(Sndb(1))  (22)

In equations (21) and (22) the terms max(Sndb(1)) and min(Sndb(1)) denote the maximum and minimum components of the vector Sndb at k=1, respectively, when signals are provided to the transmission lines at the maximum power level. The term min(Sndb(k_(max))) denotes the maximum component of the vector Sndb when the iterative method has reached sufficient convergence meaning min(Sndb(k_(max))) max(Sndb(k_(max))). The definitions of the variables a and b are also illustrated in FIG. 8.

If FEXT does not occur, the variable η is one. The higher the presence of FEXT, the more the variable η decreases.

In the following a further iterative method according to one embodiment is described which improves the signal-to-noise ratios of the shorter transmission lines compared to the iterative method described above. The improvement is achieved by successively increasing the input power levels of the signals provided to the transmission lines L₁ to L_(M-1) until the logarithmic signal-to-noise ratio obtained from at least one transmission line, which is usually the longest transmission line L_(M), falls below a predetermined threshold value Sndb_(min). The input power level of the signals provided to the longest transmission line L_(M) is kept constant.

Before starting the iterative method presented in the following input power levels {tilde over (p)}(0)_(i) (i=1, . . . , M) must be known, which, when used for providing signals to the transmission lines L₁ to L_(M), produce equal logarithmic signal-to-noise ratios at the output terminals of the transmission lines L₁ to L_(M). For example, the input power levels {tilde over (p)}(0)_(i) are given by the input power levels p(k_(max))_(i), which are obtained in the final iteration cycle k_(max) of the iterative method presented above and which produced an equal logarithmic signal-to-noise ratio Sndb(k_(max))_(i) for all transmission lines L₁ to L_(M).

Starting from the input power levels {tilde over (p)}(0)_(i), the input power levels are successively increased at each iteration cycle until the logarithmic signal-to-noise ratio measured at the output terminal of at least one transmission line L_(i) is reduced by more than a predetermined parameter Δdb compared to the logarithmic signal-to-noise level Sndb(k_(max))_(i).

According to one embodiment, before starting the iterative method it is verified whether Δdb<b−a. If this inequation is false, the maximum power level p_(max) is chosen for all of the transmission lines L₁ to L_(M) and the iterative method is not performed any further. If the inequation is true, the iterative method is started.

The iteration cycles of the method are denoted with {tilde over (k)} (=1, 2, . . . ). At the beginning of each iteration cycle signals are provided to the input terminals of the transmission lines L₁ to L_(M). The signals are received at the output terminals of the transmission lines L₁ to L_(M) and the logarithmic signal-to-noise ratios Sndb(k)_(i) are measured for each signal. The input power levels {tilde over (p)}({tilde over (k)}) for each iteration cycle {tilde over (k)} are given by the following equations:

$\begin{matrix} {{\overset{\sim}{p}\left( \overset{\sim}{k} \right)} = \begin{bmatrix} {\overset{\sim}{p}\left( \overset{\sim}{k} \right)}_{1} \\ {\overset{\sim}{p}\left( \overset{\sim}{k} \right)}_{2} \\ \vdots \\ {\overset{\sim}{p}\left( \overset{\sim}{k} \right)}_{M} \end{bmatrix}} & (23) \\ {{\overset{\sim}{p}\left( {\overset{\sim}{k} + 1} \right)} = {{\overset{\sim}{p}\left( \overset{\sim}{k} \right)} \cdot {{1 - {\overset{\sim}{g} \cdot {\overset{\sim}{d}\left( \overset{\sim}{k} \right)}}}}}} & (24) \\ {{\overset{\sim}{p}(0)} = {{p\left( k_{\max} \right)}.}} & (25) \end{matrix}$

In equation (24) {tilde over (g)} is a predetermined constant, which influences the convergence of the method, and {tilde over (d)}({tilde over (k)}) is a vector of functions {tilde over (F)} of the input power levels {tilde over (p)}({tilde over (k)})_(i), which will be discussed in more detail later:

$\begin{matrix} {{\overset{\sim}{d}\left( \overset{\sim}{k} \right)}_{i} = {\overset{\sim}{F}\left( \frac{{\overset{\sim}{p}\left( \overset{\sim}{k} \right)}_{i}}{p_{\max}} \right)}} & (26) \end{matrix}$

Before the input power levels {tilde over (p)}({tilde over (k)}+1)_(i) are used for providing signals to the transmission lines L₁ to L_(M), the vector {tilde over (p)}({tilde over (k)}+1) may be scaled:

$\begin{matrix} {{\overset{\hat{\sim}}{p}\left( {\overset{\sim}{k} + 1} \right)} = {{\overset{\sim}{p}\left( {\overset{\sim}{k} + 1} \right)} \cdot \frac{p_{\max}}{\max \left( {\overset{\sim}{p}\left( {\overset{\sim}{k} + 1} \right)} \right)}}} & (27) \end{matrix}$

In equation (27) max({tilde over (p)}({tilde over (k)}+1)) denotes the maximum component of the vector {tilde over (p)}({tilde over (k)}+1). The scaled vector {tilde over ({circumflex over (p)}({tilde over (k)}+1) is used for transmitting signals during the iteration cycle {tilde over (k)}+1 over the transmission lines L₁ to L_(M). Scaling causes the input power level {tilde over ({circumflex over (p)}({tilde over (k)}+1)_(M) of the longest transmission line L_(M) to be constant.

According to a further embodiment, the vector p(k+1) of equation (24) is shifted once more:

{tilde over ({tilde over (p)}({tilde over (k)}+1)=|{tilde over (p)}({tilde over (k)}+1)−{tilde over ({tilde over (g)}·{tilde over (d)}({tilde over (k)})·p _(max)|  (28)

In equation (28) {tilde over ({tilde over (g)} is a predetermined constant. The vector {tilde over ({tilde over (p)}({tilde over (k)}+1) may be scaled:

$\begin{matrix} {{\hat{\overset{\sim}{\overset{\sim}{p}}}\left( {\overset{\sim}{k} + 1} \right)} = {{\overset{\sim}{\overset{\sim}{p}}\left( {\overset{\sim}{k} + 1} \right)} \cdot \frac{p_{\max}}{\max \left( {\overset{\sim}{\overset{\sim}{p}}\left( {\overset{\sim}{k} + 1} \right)} \right)}}} & (29) \end{matrix}$

The termination condition of the iterative method is:

min(Sndb({tilde over (k)} _(max))_(i))<min(Sndb(k _(max)))−Δdb  (30)

According to equation (30) the iterative method is terminated or at least interrupted if at least one of the measured logarithmic signal-to-noise ratios at a iteration cycle {tilde over (k)}_(max) falls below the difference min(Sndb(k_(max)))−Δdb. In this case the iterative method is either terminated or it is started again with smaller constants {tilde over (g)} and {tilde over ({tilde over (g)}. For restarting the iterative method input power levels {tilde over (p)}({tilde over (k)}<{tilde over (k)}_(max)) are used.

In the following a simulation is presented which illustrates the iterative method described above. The simulated network is a VDSL network and comprises 25 transmission lines L₁ to L₂₅ in a cable C. The lengths of the transmission lines L₁ to L₂₅ are evenly distributed between 200 m and 700 m. The network is based on a model as shown in FIG. 3. The type of interference is self-FEXT and alien noise. The parameter Δdb is set to 3 dB. For the function {tilde over (F)} (cf. equation (26)) a linear function, a exponential function and a logarithmic function are chosen:

$\begin{matrix} {{\overset{\sim}{F}\left( \frac{{\overset{\sim}{p}\left( \overset{\sim}{k} \right)}_{i}}{p_{\max}} \right)} = \frac{{\overset{\sim}{p}\left( \overset{\sim}{k} \right)}_{i}}{p_{\max}}} & (31) \\ {{\overset{\sim}{F}\left( \frac{{\overset{\sim}{p}\left( \overset{\sim}{k} \right)}_{i}}{p_{\max}} \right)} = 100^{\frac{{\overset{\sim}{p}{(\overset{\sim}{k})}}_{i}}{p_{\max}}}} & (32) \\ {{\overset{\sim}{F}\left( \frac{{\overset{\sim}{p}\left( \overset{\sim}{k} \right)}_{i}}{p_{\max}} \right)} = {\log_{10}\left( \frac{{\overset{\sim}{p}\left( \overset{\sim}{k} \right)}_{i}}{p_{\max}} \right)}} & (33) \end{matrix}$

FIG. 9 shows a plot of the input power level p versus the length l of the transmission lines L₁ to L₂₅ and a plot of the resulting logarithmic signal-to-noise ratio Sndb versus the length l in the presence of FEXT and alien noise. The three functions {tilde over (F)} according to equations (31) to (33) were used for the simulation. It is evident from FIG. 9 that performing the iterative method described above results in better logarithmic signal-to-noise ratios for shorter transmission lines, whereas the signal-to-noise ratios of the longer transmission lines are only slightly decreased.

So far, methods for determining input power levels for a single frequency channel were discussed. In order to adjust the total power spectrum density of all modems, the described iterative methods may be performed for all frequency channels. For that, signals of different frequency channels can be transmitted over the transmission lines simultaneously.

In the following another example is presented in order to demonstrate the performance of the iterative methods discussed above. The example is based on a VDSL network having a frequency band allocation as shown in FIG. 10. The maximum input power level is the same for all frequency channels. The maximum power spectrum density is −59 dBm/Hz. In this example only the upstream direction is considered. The assumed power spectral density of the alien noise is shown in FIG. 11. All interference signals caused by alien noise have the same power level. The alien noise is superposed by an additional white noise signal having a power spectral density of −140 dBm/Hz. The simulated network comprises 25 transmission lines L₁ to L₂₅ in a cable C. The lengths of the transmission lines L₁ to L₂₅ are evenly distributed between 200 m and 600 m. FIG. 12 shows the line attenuation of the shortest and the longest transmission line. FIG. 13 shows the minimum and maximum FEXT attenuation. The factor K_(ij) is constant.

The predetermined parameter Δdb is modified in order to be dependent on the fraction of the alien noise. The modified parameter Δ db(f) is calculated for each frequency channel as follows:

$\begin{matrix} {{\Delta {\overset{\_}{db}(f)}} = {{\left( \frac{\eta (f)}{\eta_{\max}} \right)^{4} \cdot \Delta}\; {{db}.}}} & (34) \end{matrix}$

FIGS. 14 and 15 illustrate the results of the simulation. The input power levels p for each of the transmission lines L₁ to L₂₅ are shown. The maximum bit rates for each of the transmission lines L₁ to L₂₅ are also shown. The maximum bit rates were calculated by adding the maximum bit rates of each frequency channel, which were derived from the logarithmic signal-to-noise ratios. The parameter Δdb was set to 3 dB for the simulation illustrated in FIG. 14 and 6 dB for the simulation illustrated in FIG. 15. FIG. 16 shows the spectral power density of the shortest and the longest transmission line for Δdb=3 dB and Δdb=6 dB.

FIG. 17 illustrates the results of another simulation. Here, the transmission lines L₁ to L₂₅ have lengths between 200 m and 600 m, which are statistically distributed. The factor K_(ij) and the alien noise are also statistically distributed to a certain degree. The parameter Δdb was set to 6 dB.

In addition, while a particular feature or aspect of an embodiment may have been disclosed with respect to only one of several implementations, such feature or aspect may be combined with one or more other features or aspects of the other implementations as may be desired and advantageous for any given or particular application. Furthermore, to the extent that the terms “include”, “have”, “with”, or other variants thereof are used in either the detailed description or the claims, such terms are intended to be inclusive in a manner similar to the term “comprise”. The terms “coupled” and “connected”, along with derivatives may have been used. It should be understood that these terms may have been used to indicate that two elements co-operate or interact with each other regardless whether they are in direct physical or electrical contact, or they are not in direct contact with each other. Furthermore, it should be understood that embodiments may be implemented in discrete circuits, partially integrated circuits or fully integrated circuits or programming means. Also, the term “exemplary” is merely meant as an example, rather than the best or optimal. It is also to be appreciated that features and/or elements depicted herein are illustrated with particular dimensions relative to one another for purposes of simplicity and ease of understanding, and that actual dimensions may differ substantially from that illustrated herein. 

1. A method, wherein the following steps are iteratively repeated: providing a plurality of signals at a respective one of a plurality of transmission links, the transmission links being wired lines wherein neighboring ones of the transmission links are distorted by cross-talk interference; transmitting the plurality of signals over the respective one of the plurality of transmission links; and measuring signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links, wherein an input power level of the plurality of signals is set such that the signal-to-noise ratios of the plurality of signals converge when measured after their transmission over the plurality of transmission links, wherein, for at least one iteration cycle, the input power level of the plurality of signals when provided at the respective one of the plurality of transmission links depends on a difference of the measured signal-to-noise ratio of the signal transmitted over the respective one of the plurality of transmission links during a previous iteration cycle.
 2. The method of claim 1, wherein the input power level of the plurality of signals further depends on the measured signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links during a previous iteration cycle.
 3. The method of claim 1, wherein, at least one iteration cycle, the input power level of the plurality of signals when provided at the respective one of the plurality of transmission links further depends on an average value of the measured signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links during a previous iteration cycle.
 4. The method of claim 1, wherein the input power level of the plurality of signals when provided at the respective one of the plurality of transmission links further depends on a product having at least a first factor and a second factor; wherein the first factor depends on the input power level of the signal provided at the respective one of the plurality of transmission links during a previous iteration cycle; and the second factor depends on the difference of the measured signal-to-noise ratio of the signal transmitted over the respective one of the plurality of transmission links during the previous iteration cycle and an average value of the measured signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links during the previous iteration cycle.
 5. The method of claim 1, wherein the input power level of the plurality of signals is predetermined at a first iteration cycle.
 6. The method of claim 1, wherein the input power level of the plurality of signals is set to the highest input power level at a first iteration cycle.
 7. The method of claim 1, wherein the input power level of the plurality of signals when provided to the respective one of the plurality of transmission links during a second iteration cycle depends on an inverted value of the measured signal-to-noise ratio of the signal transmitted over the respective one of the plurality of transmission links during a first iteration cycle.
 8. The method of claim 1, wherein the plurality of signals is transmitted in an upstream direction over a respective one of the plurality of transmission links.
 9. The method of claim 1, wherein the input power levels, at which the signal-to-noise ratios converge, are used for transmitting further signals.
 10. The method of claim 1, wherein the method is performed when initializing the plurality of transmission links.
 11. A method, wherein the following steps are iteratively repeated: providing a plurality of signals at a respective one of a plurality of transmission links, the transmission links being wired lines wherein neighboring ones of the transmission links are distorted by cross-talk interference; transmitting the plurality of signals over the respective one of the plurality of transmission links; and measuring signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links, wherein an input power level of the plurality of signals is set such that the signal-to-noise ratios of the plurality of signals converge when measured after their transmission over the plurality of transmission links, wherein, for at least one iteration cycle, the input power level of the plurality of signals when provided at the respective one of the plurality of transmission links depends on an average value of the measured signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links during a previous iteration cycle.
 12. The method of claim 11, wherein the input power level of the plurality of signals when provided at the respective one of the plurality of transmission links further depends on a product having at least a first factor and a second factor; wherein the first factor depends on the input power level of the signal provided at the respective one of the plurality of transmission links during a previous iteration cycle; and the second factor depends on a difference of the measured signal-to-noise ratio of the signal transmitted over the respective one of the plurality of transmission links during the previous iteration cycle and the average value of the measured signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links during the previous iteration cycle.
 13. The method of claim 11, wherein the input power level of the plurality of signals is predetermined at a first iteration cycle.
 14. The method of claim 11, wherein the input power level of the plurality of signals is set to the highest input power level at a first iteration cycle.
 15. The method of claim 11, wherein the input power level of the plurality of signals when provided to the respective one of the plurality of transmission links during a second iteration cycle depends on an inverted value of the measured signal-to-noise ratio of the signal transmitted over the respective one of the plurality of transmission links during a first iteration cycle.
 16. The method of claim 11, wherein the plurality of signals is transmitted in an upstream direction over a respective one of the plurality of transmission links.
 17. The method of claim 11, wherein the input power levels, at which the signal-to-noise ratios converge, are used for transmitting further signals.
 18. The method of claim 11, wherein the method is performed when initializing the plurality of transmission links.
 19. A device, comprising: a plurality of output terminals to provide a plurality of signals to a plurality of transmission links, the transmission links being wired lines wherein neighboring ones of the transmission lines are distorted by cross-talk interference; a plurality of input terminals to receive signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links; and a plurality of setting circuits configured to set input power levels of the plurality of signals provided to the plurality of transmission lines, wherein the input power level of the plurality of signals is set such that the signal-to-noise ratios of the plurality of signals converge when measured after their transmission over the plurality of transmission links, and wherein the plurality of setting circuits are further configured to set input power levels of the plurality of signals based on a difference of the measured signal-to-noise ratio of the signal transmitted over the respective one of the plurality of transmission links during a previous iteration cycle.
 20. A device, comprising: a plurality of output terminals to provide a plurality of signals to a plurality of transmission links, the transmission links being wired lines wherein neighboring ones of the transmission lines are distorted by cross-talk interference; a plurality of input terminals to receive signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links; and a plurality of setting circuits configured to set input power levels of the plurality of signals provided to the plurality of transmission lines, wherein the input power level of the plurality of signals is set such that the signal-to-noise ratios of the plurality of signals converge when measured after their transmission over the plurality of transmission links, and wherein the plurality of setting circuits are further configured to set input power levels based on an average value of the measured signal-to-noise ratios of the plurality of signals transmitted over the plurality of transmission links during a previous iteration cycle. 